A study of the effects of time aggregation and overlapping within the framework of IEC standards for the measurement of harmonics and interharmonics

applied sciences Article A Study of the Effects of Time Aggregation and Overlapping within the Framework of IEC Standards for the Measurement of Harmonics and Interharmonics Angel Arranz-Gimon 1, Angel Zorita-Lamadrid 2, Daniel Morinigo-Sotelo 2and Oscar Duque-Perez 2,* 1 Department of Electronic Technology, Universidad de Valladolid, 47011 Valladolid, Spain; [email protected] 2Department of Electrical Engineering, Research group ADIRE, ITAP, Universidad de Valladolid, 47011 Valladolid, Spain; [email protected] (A.Z.-L.); [email protected] (D.M.-S.) *Correspondence: oscar[email protected]; Tel.: +34 983184533 Received: 23 September 2019; Accepted: 24 October 2019; Published: 26 October 2019   Abstract: The increasing incorporation of power electronics and other non-linear loads, in addition to their energy advantages, also implies a poor power quality, especially as regards harmonic pollution. Different solutions have been proposed to measure harmonic content, taking the International Electrotechnical Commission (IEC) standards as a reference. However, there are still some issues related to the measurement of the harmonic, and especially, interharmonic content. Some of those questions are addressed in this work, such as the problem derived from the instability of the values obtained by applying the discrete Fourier transform to each sampling window, or the appearance of local peaks when there are tones separated by multiples of the resolution. Solutions were proposed based on time aggregation and the overlapping of windows. The results demonstrate that aggregation time, window type, and overlapping can improve the accuracy in harmonic measurement using Fourier transform-based methods, as defined in the standards. The paper shows the need to consider spectral and time groupings together, improving results by using an appropriate percentage of overlap and an adaptation of the aggregation time to the harmonic content. Keywords: Harmonic analysis; interharmonics; spectral leakage; rectangular window; Hann window; time aggregation; overlapping; power quality 1. Introduction Power quality is an essential feature in modern electrical systems. The increase in the number of time-variant and non-linear loads and the proliferation of distributed generation is affecting the performance of electric networks [ 1 , 2 ]. One of the main aspects to take care of is the harmonic content. Nonlinear loads and switched devices produce harmonics and interharmonics, increasing energy losses and producing measurement errors, equipment overheating, communication interferences, and light flicker [ 3 , 4 ]. New technologies, such as smart metering, renewable energy sources, electric vehicles, and other end-user equipment connected to the grid through static converters are responsible for interharmonic emissions in the range above 2 kHz (known as supraharmonics); thus, expanding the interest of researchers on energy quality [5,6]. With the increase of non-linear loads in power systems, interharmonics are becoming a growing concern [ 7 , 8 ]. The presence of interharmonics complicates the analysis and measurement due to the change of the periodicity of the waveform and a greater sensitivity to desynchronization problems. All this leads to the appearance of spectral leakage when applying methods based on the Fourier Appl. Sci. 2019,9, 4549; doi:10.3390/app9214549 www.mdpi.com/journal/applsci Appl. Sci. 2019,9, 4549 2 of 21 transform, giving rise to instability and unreliability in the RMS (Root Mean Squared) values obtained by interacting with the leakage produced by nearby interharmonics. In recent years, several signal processing methods have been proposed to enhance the identification of the interharmonic content [ 9 – 12 ]. Fourier transform, wavelet transform, Hilbert–Huang transform, and Chirp z-transform are the main non-parametric methods applied to power system waveform analysis. Parametric methods have been proposed too to perform the analysis, such as Kalman filters, ESPRIT (estimation of signal parameters by rotational invariance technique), MUSIC (multiple signal classification), and the Prony method. Hybrid methods provide high-frequency resolution and better estimation accuracy. Other modern techniques, such as enhanced the phase locked loop (EPLL), artificial neural network, and adaptive linear neural network (ADALINE) have also been used in power quality analysis. Parametric methods achieve higher frequency resolution, with tracking capabilities for time-varying harmonics and interharmonics, and are more suitable for interharmonic measurement than non-parametric methods. However, according to [ 11 ], these algorithms are time-consuming and not robust to noise and outliers, and their performance depends on the prior information of the order of the model. Non-parametric methods estimate harmonics directly from the signal, being less computationally expensive and easier to apply than parametric or hybrid methods [ 12 ]. The most common non-parametric method is the discrete Fourier transform (DFT), which is sufficiently robust and time-efficient, which justifies the use of DFT-based methods in power quality analyzers. However, the signal sampling time limits the frequency resolution and it may suffer from spectral leakage caused by fundamental frequency deviation and interharmonics [11]. The International Electrotechnical Commission (IEC) standards 61000-4-7 [ 13 ] and 61000-4-30 [ 14 ], propose the use of the DFT transform and describe the spectral and time groupings required to perform power quality measurements. Harmonic and interharmonic grouping simplifies the need to know the frequency location and amplitude of a single component. With frequency grouping, the 61000-4-7 standard aims to collect most of the spectral leakage produced within each group, minimizing the error due to this leakage that spreads out of the group, (although it also picks up more spectral leakage from outside of the group). Time grouping, contemplated in standard 61000-4-30, partially solves the information loss due to leakage, increasing the accuracy, especially in the total power, and thus minimizing the error due to the lack of stationarity of the signal. Besides, time aggregation also compresses the information [15] and reduces the effects of noise present in the signal. These standards are based on the application of the DFT transform with a rectangular window (RW) and a resolution or basic frequency of 5 Hz, for obtaining the RMS values of the harmonic and interharmonic groupings. The spectral leakage generated by the interharmonic tones (and, in general, by the tones not synchronized with the basic frequency) is its primary disadvantage. The main means to reduce this leakage are the correct synchronization of the acquisition windows to the fundamental, and the use of Hann windows (HW) only in the case of loss of synchronism. The performance of RW versus HW to minimize the effect of leakage is discussed in [ 15 – 20 ], where the results are compared to each of the frequency groupings defined in standard 61000-4 7. However, they do not present the development of the complete standard, taking into account the time grouping also described in standard 61000-4 30 and considering spectral and time groupings altogether, as it is done in this article. Many other authors studied and use methods based on IEC standards. In [ 21 – 23 ], various DFT calculation methods are compared in the framework of IEC standards. In other articles, the IEC standard is used as a single method of measuring frequencies above 2 kHz [ 6 , 24 , 25 ] or as a reference technique to compare with other new high-frequency measurement methods [ 26 – 29 ]. Additionally, based on the IEC standards, in [ 30 ], the harmonic and interharmonic subgroups generated at the input of variable speed drives are analyzed; a fixed window width (tw) of 0.2 s and a fixed total aggregation time (Tw) of 3 s are used. Oliveira, Anesio, et al. study in [ 31 ] a methodology to identify the most appropriate sampling window to quantify harmonic and interharmonic emissions, considering variable signals in time, based on the calculation of harmonic and interharmonic distortions using the DFT according to IEC 61000-4-7. Bartman and Kwiatkowski in [ 32 ] compare the results obtained Appl. Sci. 2019,9, 4549 3 of 21 with different total aggregation times, testing from windows of 0.2 s without time grouping to a total aggregation time of 3 s, as indicated in standard 61000-4-30. Despite the works previously mentioned, the selection of an adequate aggregation time is still a challenge, as it is necessary to determine an appropriate value for the total aggregation time, which, according to the harmonic content of the analyzed signal, stabilizes and improves the accuracy of the results obtained with the DFT along the successive analysis windows. This is one of the main contributions of this paper: to demonstrate the improvement that involves an adequate time aggregation obtaining more reliable and accurate measures in all the RMS values calculated with the DFT for each spectral bar. This improvement can be extended to all the harmonic groupings and distortion rates defined in the standard and formed by those spectral bars [ 6 , 25 , 29 , 33 ], and to the distortion rates proposed by other authors and based on the same standard [6,33–37]. The signal processing recommended in the standards is aimed at standardizing, simplifying, and unifying the way of measuring signals from the supply network [ 21 ]. Nevertheless, there are many practical situations where the harmonic content differs significantly from the one in the supply network. A widespread example is a measurement in the output of frequency converters for controlling electric motors, whose harmonic contents differ in the low, and mainly, in the high-frequency range due to the modulation techniques used in the equipment [ 30 , 38 , 39 ]. These motor power signals present rich harmonic content, with multiple interharmonic tones, and in many cases, with amplitudes similar to those of their closest harmonics. These near-tone situations, whose leakage may interact, occur especially in frequency converters that use modulations, such as closed-loop [ 40 ] or random-type [ 41 , 42 ], or when connected to faulty motors which cause additional harmonic content [43–45]. This paper analyzes a problem caused by spectral leakage when IEC-based groups are obtained, especially when these are obtained from measurements on signals such as the output of electronic converters. The variability and unreliability of the RMS values obtained with the DFT in the successive sampling windows is the problem. This problem is caused by the interaction of the leakage produced by nearby tones when some of them are interharmonic tones not synchronized with the sampling window and of relatively large magnitude. It will be demonstrated how the time grouping and the choice of appropriate aggregation times specific to the type of signals measured at the output of inverters, and therefore adapting well those proposed in the regulations—will make it possible to reduce the effect of these variations due to leakage. A second problem, related to the previous one, is the appearance of singularities or local peaks, due to interharmonic tones separated from each other by multiples of the spectral resolution and not affected by time aggregation as a way of obtaining a reliable RMS value. To correct this problem, this study developed a solution by aggregating with overlapping windows, that being the second main contribution of this paper. The method proposed in this article improves harmonic and interharmonic identification using DFT-based methods, such as those defined in IEC standards, reducing spectral leakage effects by selecting a proper aggregation time. The proposed method also eliminates local peaks that appear in sensitivity curves by using overlapping windows. The proposed method was validated using synthetic signals and real signals coming from an induction motor, showing the advantages of this method over the one window DFT. Results demonstrate that, through the selection of an adequate aggregation time with an appropriate percentage of overlap, a response closer to the ideal can be achieved in all the frequency groupings defined in the standards; thus, more reliable and accurate measurements can be obtained in their related distortion rates. The rest of this paper is organized as follows: Section 2presents the problems of calculating amplitudes with DFT; these problems are caused by the interaction between several nearby tones, where at least one is not synchronized with the sampling window. First, a concrete case is examined, based on one of the examples described in the annex of standard 61000-4-7. General cases with any positions of frequencies are considered later, using the rectangular window. Next, in Section 3, a solution that minimizes these problems is studied using a simple and easy-to-implement technique, Appl. Sci. 2019,9, 4549 4 of 21 such as time aggregation. This study is expanded in Section 4by comparing the use of rectangular and Hann windows when several nearby tones interact. Then, in Section 5, particular cases not solved by time aggregation are studied, such as local peaks due to interharmonic tones separated by multiples of the frequency resolution. A solution to this new problem is developed based on time aggregation with overlapping between successive analyzed windows. Section 6presents and analyzes experimental results, testing an induction, motor-fed with inverters with different harmonic contents, verifying that the aggregation time needed to stabilize the measurements depends on the harmonic content. Finally, the discussion and conclusions reached in this study are addressed in Section 7. 2. The Effects on Amplitude Due to Interactions between Tones In this section, the problems derived when the DFT is performed following the indications of the IEC standard and when there is an interaction of the spectral leakage generated by nearby tones—are studied. First, a specific case based on an example proposed in the standard with several tones in fixed positions is analyzed. Next, some cases are studied with the rectangular window where the position between the different tones that interact is changed. 2.1. Analysis of the Effects of the Interaction between Tones Spectral leakage is produced by interharmonic components of the signal or by desynchronization of the fundamental frequency (and all their integer multiples) to the sample window. To avoid spectral leakage when applying DFT, the sampling window must contain an integer multiple of all the periods of the frequency components of the signal. Optimally, this window is calculated as the minimum common multiple of all the contained periods and the resolution specified by IEC standards (5 Hz). The interharmonics can be due to the desynchronization of the fundamental with the sampling tw window (and consequently of all its multiples or harmonics), or due to actual interharmonic components, such as those generated by variable and non-linear loads, such as frequency converters. If the existing harmonics and interharmonics in the signal are all multiples of the spectral resolution (of 5 Hz, for example), or if only one tone is taken into account, the possible time aggregation benefits are not appreciated, since the same absolute values are obtained with the DFT applied to every window, as in the cases analyzed in [ 16 , 17 , 19 , 20 ]. However, it will then be proven that the absolute value of the total vector changes if successive sampling windows of a signal with several nearby tones are analyzed. The spectral leakage of these tones may interact, as it is the case in signals composed by a harmonic tone and an interharmonic tone generating leakage. This variability is explained by the addition of the leakage vector to the fixed harmonic tone vector. The leakage vector rotates because its offset at the beginning of each window change. An example was proposed, based on one described in the standard IEC 61000-4-7, Appendix C.4, to analyze the interaction between harmonic tones and the leakage produced by nearby interharmonics, and their relationship with time aggregation. A voltage waveform (Figure 1) with a 5th harmonic of 13.2 V, a 6th one of 10 V, and an interharmonic of 9.8 V at 253.3 Hz is considered. This interharmonic was added to the example of the standard since it is close to the 5th harmonic and far from the 6th one. This way, the effects of the relative situation between the leakage receiver harmonics and the interharmonics producing the leakage could be better observed. Figure 1shows the waveform of the signal in the time domain and the spectrum obtained using the DFT with a 0.6 s rectangular window. As the window used contained complete periods of all the components of the signal, no spectral leakage was observed. This ideal window was selected considering that the minimum common multiple of 250, 253.3, 300, and 5 Hz is 1.6 Hz. This ideal period (Tw) was also chosen as a multiple of 1/5 Hz =0.2 s so it could be synchronized with the window size proposed in the standard. However, the harmonic composition of a signal is usually unknown, and following IEC standards, it was analyzed in successive short windows of 0.2 s, with leakage generally appearing in each of them. Therefore, total vectors with varying amplitudes in each successive short window analyzed were Appl. Sci. 2019,9, 4549 5 of 21 obtained, due to the combination of representative vectors, which rotate at different speeds. The reason for choosing this short window size was the non-stationary nature of the signals analyzed and the time-resolution improvement at the cost of worsening the frequency resolution (uncertainty principle). Appl. Sci. 2019, 9, x FOR PEER REVIEW 5 of 21 However, the harmonic composition of a signal is usually unknown, and following IEC standards, it was analyzed in successive short windows of 0.2 s, with leakage generally appearing in each of them. Therefore, total vectors with varying amplitudes in each successive short window analyzed were obtained, due to the combination of representative vectors, which rotate at different speeds. The reason for choosing this short window size was the non-stationary nature of the signals analyzed and the time-resolution improvement at the cost of worsening the frequency resolution (uncertainty principle). Figure 1. Example with signal composed by 5th and 6th harmonics and an interharmonic at 253.3 Hz: (a) waveform in the time domain, and (b) spectrum after using the discrete Fourier transform (DFT) in a single window of total aggregation time (Tw) = 0.6 s. These changes of amplitude are illustrated in Figure 2a with the spectra for the first three short windows of the example of Figure 1. It can be observed how the total amplitude measured at the 250 Hz spectral bar changed since in that position the 5th harmonic and the leakage received from the close interharmonic at 253.3 Hz were added. The resulting vector oscillated between the sum of the modules or their difference, depending on the phase angle between the leakage vectors and the harmonic. The cycle was repeated every three windows, as can be expected since the ideal period in this example (Tw = 0.6 s.) is three short windows. In Figure 2, minor amplitude changes in the position of the farthest 6th harmonic can be seen. These changes are much smaller in the rest of the spectral bars, which only contain the received leakage (as can be seen in the resulting value of the interharmonic group gIH5). Figure 2. DFT on successive windows of 0.2 s of the signal of the example of Figure 1: (a) modules obtained, and (b) vector evolution of the 5th harmonic and its sum with the leakage received in the spectral bar of 250 Hz. Therefore, the most important variations occur in the spectral bars corresponding to the harmonics closest to the interharmonics that generate spectral leakage when the DFT is applied to Figure 1. Example with signal composed by 5th and 6th harmonics and an interharmonic at 253.3 Hz: ( a ) waveform in the time domain, and ( b ) spectrum after using the discrete Fourier transform (DFT) in a single window of total aggregation time (Tw)=0.6 s. These changes of amplitude are illustrated in Figure 2a with the spectra for the first three short windows of the example of Figure 1. It can be observed how the total amplitude measured at the 250 Hz spectral bar changed since in that position the 5th harmonic and the leakage received from the close interharmonic at 253.3 Hz were added. The resulting vector oscillated between the sum of the modules or their difference, depending on the phase angle between the leakage vectors and the harmonic. The cycle was repeated every three windows, as can be expected since the ideal period in this example (Tw =0.6 s.) is three short windows. In Figure 2, minor amplitude changes in the position of the farthest 6th harmonic can be seen. These changes are much smaller in the rest of the spectral bars, which only contain the received leakage (as can be seen in the resulting value of the interharmonic group gIH5). Appl. Sci. 2019, 9, x FOR PEER REVIEW 5 of 21 However, the harmonic composition of a signal is usually unknown, and following IEC standards, it was analyzed in successive short windows of 0.2 s, with leakage generally appearing in each of them. Therefore, total vectors with varying amplitudes in each successive short window analyzed were obtained, due to the combination of representative vectors, which rotate at different speeds. The reason for choosing this short window size was the non-stationary nature of the signals analyzed and the time-resolution improvement at the cost of worsening the frequency resolution (uncertainty principle). Figure 1. Example with signal composed by 5th and 6th harmonics and an interharmonic at 253.3 Hz: (a) waveform in the time domain, and (b) spectrum after using the discrete Fourier transform (DFT) in a single window of total aggregation time (Tw) = 0.6 s. These changes of amplitude are illustrated in Figure 2a with the spectra for the first three short windows of the example of Figure 1. It can be observed how the total amplitude measured at the 250 Hz spectral bar changed since in that position the 5th harmonic and the leakage received from the close interharmonic at 253.3 Hz were added. The resulting vector oscillated between the sum of the modules or their difference, depending on the phase angle between the leakage vectors and the harmonic. The cycle was repeated every three windows, as can be expected since the ideal period in this example (Tw = 0.6 s.) is three short windows. In Figure 2, minor amplitude changes in the position of the farthest 6th harmonic can be seen. These changes are much smaller in the rest of the spectral bars, which only contain the received leakage (as can be seen in the resulting value of the interharmonic group gIH5). Figure 2. DFT on successive windows of 0.2 s of the signal of the example of Figure 1: (a) modules obtained, and (b) vector evolution of the 5th harmonic and its sum with the leakage received in the spectral bar of 250 Hz. Therefore, the most important variations occur in the spectral bars corresponding to the harmonics closest to the interharmonics that generate spectral leakage when the DFT is applied to Figure 2. DFT on successive windows of 0.2 s of the signal of the example of Figure 1: ( a ) modules obtained, and ( b ) vector evolution of the 5th harmonic and its sum with the leakage received in the spectral bar of 250 Hz. Therefore, the most important variations occur in the spectral bars corresponding to the harmonics closest to the interharmonics that generate spectral leakage when the DFT is applied to successive time windows. In these spectral bars, the leakage is projected on the fixed vector of the harmonic. The Appl. Sci. 2019,9, 4549 6 of 21 spectral leakage phase is variable, so the resulting vector at the frequency of the harmonic can change considerably between successive collected windows, as illustrated in Figure 2b. It should be noted that the amplitudes of vectors represent the RMS values of the different measured frequency components. Since leakage reduction is not always possible, at least the RMS value found measuring the harmonic content of each spectral bar must be stable and as close as possible to the RMS value of all the components added in that bar (or common RMS, according to the standard IEC 61000-4-7, Appendix C.4). This common RMS is obtained as the square root of the sum of squares of the modules of the components x and y that add up in this spectral bar, px2+y2 ; in this example, √13.22+4.052= 13.808 V . As can be seen in Figure 2, the values of the amplitude of the resulting vector in each window were generally different from the correct common RMS value and were unstable. 2.2. Analysis of Varying the Position of the Interharmonic Tone The amplitude variations that appear in the analysis of successive windows (and as a consequence of the spectral leakage produced by a single fixed interharmonic tone) were discussed in the previous section. Next, a similar analysis was made, but varying the frequency of the interharmonic tone of the previous example. The RMS value measured in the spectral bar corresponding to 250 Hz is represented in Figure 3, with a fixed harmonic tone of 13.2 V at the same frequency and a second interharmonic tone of 9.8 V with variable frequency. The values obtained with the DFT on four non-overlapping and consecutive windows 0.2 s long (tw1–tw4) are shown in that figure. These values were obtained using rectangular windows. When the harmonic and variable tones coincide at the origin of abscissa, 250 Hz, the RMS value of their vectorial sum is obtained. For the other variable tone positions that are synchronous with the tw window (or multiples of the basic frequency: 255, 260, 265 . . . Hz) the harmonic does not receive leakage, and therefore, its value remains stable at 13.2 V. The value obtained is different due to the generated leakage for the rest of the non-synchronous (or interharmonic) positions, with more significant variations the closer is the variable frequency interharmonic tone to the measured spectral bar, located at 250 Hz. Thus, the interaction between tones is more significant when both are closer together (Figure 3, 250–255 Hz spectral bar interval), and smaller variations occur when both tones are far apart (Figure 3, 260–265 Hz, 265–270 Hz). Therefore, in the analysis of a single window, the values obtained in all cases were different from the desired common RMS values, except in variable tone synchronous positions, where there was no leakage (see Figure 3a). Appl. Sci. 2019, 9, x FOR PEER REVIEW 6 of 21 successive time windows. In these spectral bars, the leakage is projected on the fixed vector of the harmonic. The spectral leakage phase is variable, so the resulting vector at the frequency of the harmonic can change considerably between successive collected windows, as illustrated in Figure 2b. It should be noted that the amplitudes of vectors represent the RMS values of the different measured frequency components. Since leakage reduction is not always possible, at least the RMS value found measuring the harmonic content of each spectral bar must be stable and as close as possible to the RMS value of all the components added in that bar (or common RMS, according to the standard IEC 61000-4-7, appendix C.4). This common RMS is obtained as the square root of the sum of squares of the modules of the components 𝒙  and 𝒚  that add up in this spectral bar, √𝑥2 + 𝑦2; in this example, √13.22 + 4.052=13.808 V. As can be seen in Figure 2, the values of the amplitude of the resulting vector in each window were generally different from the correct common RMS value and were unstable. 2.2. Analysis of Varying the Position of the Interharmonic Tone The amplitude variations that appear in the analysis of successive windows (and as a consequence of the spectral leakage produced by a single fixed interharmonic tone) were discussed in the previous section. Next, a similar analysis was made, but varying the frequency of the interharmonic tone of the previous example. The RMS value measured in the spectral bar corresponding to 250 Hz is represented in Figure 3, with a fixed harmonic tone of 13.2 V at the same frequency and a second interharmonic tone of 9.8 V with variable frequency. The values obtained with the DFT on four non-overlapping and consecutive windows 0.2 s long (tw1–tw4) are shown in that figure. These values were obtained using rectangular windows. When the harmonic and variable tones coincide at the origin of abscissa, 250 Hz, the RMS value of their vectorial sum is obtained. For the other variable tone positions that are synchronous with the tw window (or multiples of the basic frequency: 255, 260, 265 … Hz) the harmonic does not receive leakage, and therefore, its value remains stable at 13.2 V. The value obtained is different due to the generated leakage for the rest of the nonsynchronous (or interharmonic) positions, with more significant variations the closer is the variable frequency interharmonic tone to the measured spectral bar, located at 250 Hz. Thus, the interaction between tones is more significant when both are closer together (Figure 3, 250–255 Hz spectral bar interval), and smaller variations occur when both tones are far apart (Figure 3, 260–265 Hz, 265–270 Hz). Therefore, in the analysis of a single window, the values obtained in all cases were different from the desired common RMS values, except in variable tone synchronous positions, where there was no leakage (see Figure 3a). Figure 3. RMS value measured at the 250 Hz spectral bar, with a 13.2 V harmonic fixed in the same position, as a function of the 9.8 V variable frequency tone position, in several successive windows treated individually (tw1–tw4): (a) variable frequency tone positions between 250 and 270 Hz, and (b) zoomed zone between 250 and 255 Hz. Figure 3. RMS value measured at the 250 Hz spectral bar, with a 13.2 V harmonic fixed in the same position, as a function of the 9.8 V variable frequency tone position, in several successive windows treated individually (tw1–tw4): ( a ) variable frequency tone positions between 250 and 270 Hz, and (b) zoomed zone between 250 and 255 Hz. Figure 3b shows a zoom of the area between the harmonic at 250 Hz and the following spectral bar at 255 Hz. It can be seen that the values obtained are the same as in the example in the preceding section when the position of interharmonic sweeping tone was 253.3 Hz: 9.37 V in the window tw1, Appl. Sci. 2019,9, 4549 7 of 21 16.30 V in tw2, 14.78 V in tw3, 9.37 V again in the window tw4, etc. Figure 3b also highlights the position of the variable tone at 251.6 Hz. In this case, the ideal period Tw is also 0.6 s, and therefore, the RMS values found repeat every three windows. Additionally, the total spectral leakage produced was the same for the positions of the variable tone at 251.6 Hz and 253.3 Hz. However, when the tone was at 251.6 Hz, the variations in the values found in each window were higher, due to its closer proximity to the 250 Hz spectral bar, where the amplitude was actually measured. In conclusion, in the analysis of a single window, the values obtained change depending on the position of the variable tone and are different from the ones desired, except in the synchronous positions of the tone, in which there is no leakage. Moreover, for the same position of the variable tone, the values obtained are different if they are compared along successive windows, except for the positions in which the tone does not emit leakage (and in general, the positions with distances between tones are multiples of the spectral resolution), as shown in Figure 3. 3. Measurement Improvement by Time Aggregation 3.1. Calculation of the Ideal Aggregation Time to Find the Common RMS Value In the examples of the previous section, the interactions between tones (interharmonic or not synchronized with the acquisition window) were studied. These interactions are due to the spectral leakage produced by the lack of synchronism, giving rise to variations in the amplitudes of the DFT calculated in each window, and can be large in the case of proximity between tones. This can happen when signals, such as the output of electronic converters, are measured using IEC standards. Therefore, it is necessary to correct and stabilize these amplitude variations to make them as close as possible to the desired and correct common RMS value. The effects of time aggregation on the processing of frequency groupings were studied next, to demonstrate how to overcome that problem. First, it was proven that the aggregation of the RMS values found in successive windows, for two proximate tones, permits obtaining the correct RMS value of the components of these tones that interact in the same spectral bar. Let x be the harmonic component and y the leakage received by x . The RMS value of the resulting vector would ideally be equal to px2+y2 , as if the angle between the two vectors was 90 º . However, the actual phase angle between the two tones is unknown, and the procedure is to divide the time into mshort windows and to average the squares of the vectors of each window, making, therefore, a time aggregation of these values, as can be seen in Equation (1). The relative positions of the vectors are xi and yi , with a phase angle ϕi , which varies as the successive mshort time windows. sPm−1 i=0χi+yi2 m=sm·(x2+y2) + 2·x·y·Pm−1 i=0cos(ϕi) m=s(x2+y2) + 2·x·y·Pm−1 i=0cos(ϕi) m.(1) The second term in Equation (1), which depends on the successive positions of the vectors ( ϕi ), explains the fluctuations of the values, and therefore, it should be as low as possible. This can be achieved in two ways: • The term m P i=1 cos(ϕi) decreases if the total aggregation time coincides with the ideal period Tw (or a multiple), divided into m=Tw/tw =pshort windows. In that case, an integer number nof complete phase turns of the leakage (related to the other tone) is obtained. As a result, ϕi increases an average of (n · 360/p) degrees in each evaluated window, so that the resulting angle is given by Equation (2): ϕi=β+i·(n·360/p), (2) Appl. Sci. 2019,9, 4549 8 of 21 where n · 360 is the total angle rotated by the leakage vector until it is again, in the same relative position with the other harmonic vector and βis the initial phase angle. Then: m−1 X i=0 cosϕi= p−1 X i=0 cos(β+i·n·360/p)=0. (3) This way, for analysis periods equal to or multiples of the ideal Tw, divided into short windows tw, on which the DFT is performed, the common RMS values can be obtained for all the spectral components contained in that Tw period. • Increasing the number of evaluated windows, m. As vectors are added, in a quantity not multiple of pwindows, the RMS value obtained differs from the common or correct, but to a lesser extent as the number of aggregated windows, m, becomes greater. Since the actual components are unknown in real cases, the number mof aggregated windows is increased to reduce the second term in Equation (1). Next, the cases described in the previous section will be analyzed again, but now applying this solution. 3.2. The Analysis of Time Aggregation to Mitigate the Effects on Amplitude In the example proposed in Section 2.1, the appropriate number of short windows is three (p=0.6 s/0.2 s =3 windows). The only interharmonic at 253.3 Hz produces the spectral leakage. Its representative vector will rotate, relative to the position of the vector of the other component, at an average rate of (253.3–250) Hz × 0.2 s/tw × 360 /cycle =240 per short window tw. As it can be observed in Figure 2, the initial position of the leakage vector is repeated every three windows; that is, in 3 tw × 240/tw =720 (two complete turns). The speed of rotation between any two tones is just the difference of frequencies between them, which, multiplied by the ideal period Tw, gives the number of complete turns of one tone with respect to the other until the same relative position between them is reached (3.3 Hz ×0.6 s/Tw =2, in the example). For this example, Table 1shows the values obtained with each acquisition window, together with the corresponding aggregated values calculated with the modules accumulated up to each window considered, for the spectral bars corresponding to the 5th and 6th harmonics, interharmonic group 5, and the total energy (or sum of all the spectral bars, according to Parseval's theorem). Table 1. Modules obtained for each acquisition window for the total signal of Figure 1, for different frequency groupings, with and without time aggregation. Window Number 5th Harmonic (250 Hz) 6th Harmonic (300 Hz) gIH 5 (255-295 Hz) Total Vrms Aggregation Aggregation Aggregation Aggregation No Yes No Yes No Yes No Yes tw1 9.372 9.372 10.303 10.303 8.574 8.574 16.550 16.550 tw2 16.303 13.297 9.780 10.045 8.537 8.555 21.000 18.906 tw3 14.777 13.808 9.922 10.004 8.497 8.536 19.898 19.243 tw4 9.372 12.843 10.303 10.080 8.574 8.545 16.550 18.606 tw5 16.303 13.606 9.780 10.021 8.537 8.544 21.000 19.109 tw6 14.777 13.808 9.922 10.004 8.497 8.536 19.898 19.243 tw7 9.372 13.265 10.303 10.048 8.574 8.541 16.550 18.882 It can be observed how every three windows, all the values of the modules of each window repeat, and the value aggregated after this third window is repeated after three other windows and so on. Appl. Sci. 2019,9, 4549 9 of 21 The aggregated values are separated again from the ideal, common RMS value if more windows are added, but while decreasing the error, without it being necessary to stop exactly in one of the windows’ multiples of Tw to obtain a good result. The final aggregated value is still an average that approximates the desired common RMS value in all groupings, including that of the total RMS. The approximation is better, the longer the time of the aggregation. In practice, in the signals obtained from real tests, there is a limitation of this time due to the thermal constants of this type of test. Reaching the true common RMS value does not mean that an interharmonic group such as gIH5 encompasses all the energy released by the interharmonic leakage of 253.3 Hz (9.8 V), as this is only possible if a frequency grouping of the entire spectrum is considered. It means that this common RMS value is correctly measured, as the square root of the sum of squares of the modules of the components that are added in each bar are (for 5th harmonic: √13.22+4.052=13.808 V, as seen in Section 2.1). Table 1also indicates the total common RMS value of 19.243 Vrms, obtained by adding all the spectral bars and aggregating their values along three windows (which coincides exactly with the theoretical value, p13.22+9.82+102, if all the components of the studied example are considered). It can be observed that the repetition period to obtain the total common RMS value, containing all the spectral bars, is the same as for each group of frequencies, since only an interharmonic has been considered (that is the cause of the leakage that affects the whole spectrum, and therefore, rotates at the same speed in all the spectral bars). If there were multiple interharmonics, there would be areas of the spectrum with different ideal aggregation time related to other areas and the full spectrum, depending on the proximity and influence of the different interharmonics causing the spectral leakage producing this lack of synchronization. 3.3. An Analysis of Varying the Position of the Interharmonic Tone Figure 4shows the RMS value measured at the 250 Hz spectral bar, in which a harmonic tone of 13.2 Vrms is kept fixed. This value depends on the frequency of a second variable tone of 9.8 Vrms. The individual values found after performing the DFT on each of the first four windows of 0.2 s (tw1–tw4) are shown in that figure, along with those computed after performing the time aggregation on the first three windows (aggregated over time (Aggreg.) tw1–tw3), and those using a higher number of windows (Aggreg. tw1–tw144). Figure 4b shows an enlarged area with the values obtained for the sweeping tone at 253.3 Hz. The time aggregation of three windows (black dotted line) provides the correct common RMS value (13.81 V) for that position, which is also obtained if another quantity multiple of three windows is aggregated (144 in this graph, black continuous line). However, the aggregation of three windows is not sufficient for other positions of the tone closest to the harmonic with which it interacts, as it takes longer aggregation time when both tones are closer. The most significant variations between values obtained in successive windows occur when the sweeping tone is close to the center of the space between spectral bars, as in those positions, the leakage produced is the highest. Additionally, in those positions, the sum of the vector components of both tones experiences abrupt changes because the rotation speed between the representative vectors of the tones is maximum, so the variations of the phase angles between them are very significant. As the sweep tone approaches the other tone, changes in values between windows become slower, as the phase angle variation is smaller. For small rotation angles (due to the interaction between nearby tones), the evolution of the cosine summation in (1) is slower, and that leads to a more extensive aggregation of windows to improve the calculation of the RMS value. Therefore, cos( ϕi ) evolves more slowly for close tones or with low rotation speeds between them, as is observed in Figure 4b when the sweep tone is close to the fixed harmonic located at 250 Hz. In that case, there are smaller variations between the amplitudes obtained with the successive tw1–tw4 windows and a more significant difference between the aggregated value computed with only three windows and the correct RMS value (continuous black line, for a high number of aggregated windows). Appl. Sci. 2019,9, 4549 16 of 21 6. Case Study As a complement to the previous examples, in which synthetic signals based on examples appearing in the IEC Standard were used, an experimental study has been carried out. An induction motor was tested by being fed from two inverters with different harmonic contents—Allen Bradley ' s PowerFlex 40 (sinusoidal PWM modulation type) and Telemecanique ' s Altivar 66 (random carrier frequency modulation); thus, obtaining a greater variety of harmonic contents. The motor used was a Siemens 0.75 kW, star connected, with rated values of 50 Hz, 400 V, and 1.86 A. A magnetic powder brake was used as a load, adjusted so that part of the tests were carried out with low load (motor slip close to 0.3%), and others with high load (slip around 4%). The acquisition system was based on a National Instruments PCI6250 card, plus an external interface module with LEM Hall Effect sensors used as transducers. The acquired data was processed using Matlab R2015 software. The induction motor used mixed eccentricity, which produces great interharmonic content in the low part of the current spectrum, which, together with the abundant harmonic and interharmonic content in the high part of the spectrum present in the output of the inverters, allowed us analyzing situations with a multitude of nearby tones and similar amplitudes. The motor operated at steady state during 60 s long tests, and the sampling frequency was 80 kS/s. All measurements were made at the output of the inverters, with fundamental frequencies and harmonic contents different from those of the mains signal, so it was necessary to adapt the analysis system, based on IEC standards, and orient it to the measurement of the utility network; to the specific characteristics of the signals. Figure 9shows the laboratory test bench. Appl. Sci. 2019, 9, x FOR PEER REVIEW 16 of 21 PowerFlex 40 (sinusoidal PWM modulation type) and Telemecanique's Altivar 66 (random carrier frequency modulation); thus, obtaining a greater variety of harmonic contents. The motor used was a Siemens 0.75 kW, star connected, with rated values of 50 Hz, 400 V, and 1.86 A. A magnetic powder brake was used as a load, adjusted so that part of the tests were carried out with low load (motor slip close to 0.3%), and others with high load (slip around 4%). The acquisition system was based on a National Instruments PCI6250 card, plus an external interface module with LEM Hall Effect sensors used as transducers. The acquired data was processed using Matlab R2015 software. The induction motor used mixed eccentricity, which produces great interharmonic content in the low part of the current spectrum, which, together with the abundant harmonic and interharmonic content in the high part of the spectrum present in the output of the inverters, allowed us analyzing situations with a multitude of nearby tones and similar amplitudes. The motor operated at steady state during 60 s long tests, and the sampling frequency was 80 kS/s. All measurements were made at the output of the inverters, with fundamental frequencies and harmonic contents different from those of the mains signal, so it was necessary to adapt the analysis system, based on IEC standards, and orient it to the measurement of the utility network; to the specific characteristics of the signals. Figure 9 shows the laboratory test bench. Figure 9. Laboratory test bench. Figure 10a shows the low part of the frequency response of the output current of the induction motor fed by a PowerFlex inverter with slip s ≈ 4% and a fundamental frequency of 45 Hz. Figure 10b shows the low part of the frequency response of the output voltage of the Altivar inverter working at 55 Hz and with low loaded motor (s ≈ 0.3%). The frequency responses were obtained based on the IEC standard, (using DFT, with spectral bars separated by 5 Hz), not yet grouped by frequency. It can be seen that the interharmonic content was much higher for the current signal (figure 10a) than for the voltage signal (figure 10b). Therefore, high values of the groupings and current rates containing those frequencies were to be expected, and a greater interaction between tones, which motivates an increase in the aggregation time necessary to obtain stable values, as explained before. On the other hand, the tone interaction was predicted to be lower in the case of figure 10b, since the voltage measured in that zone presents practically only harmonics (which do not interact with each other, as they do not produce spectral leakage). Figure 9. Laboratory test bench. Figure 10a shows the low part of the frequency response of the output current of the induction motor fed by a PowerFlex inverter with slip s ≈ 4% and a fundamental frequency of 45 Hz. Figure 10b shows the low part of the frequency response of the output voltage of the Altivar inverter working at 55 Hz and with low loaded motor (s ≈ 0.3%). The frequency responses were obtained based on the IEC standard, (using DFT, with spectral bars separated by 5 Hz), not yet grouped by frequency. It can be seen that the interharmonic content was much higher for the current signal (Figure 10a) than for the voltage signal (Figure 10b). Therefore, high values of the groupings and current rates containing those frequencies were to be expected, and a greater interaction between tones, which motivates an increase in the aggregation time necessary to obtain stable values, as explained before. On the other hand, the tone interaction was predicted to be lower in the case of Figure 10b, since the voltage measured in that zone presents practically only harmonics (which do not interact with each other, as they do not produce spectral leakage). Appl. Sci. 2019,9, 4549 17 of 21 Appl. Sci. 2019, 9, x FOR PEER REVIEW 16 of 21 PowerFlex 40 (sinusoidal PWM modulation type) and Telemecanique's Altivar 66 (random carrier frequency modulation); thus, obtaining a greater variety of harmonic contents. The motor used was a Siemens 0.75 kW, star connected, with rated values of 50 Hz, 400 V, and 1.86 A. A magnetic powder brake was used as a load, adjusted so that part of the tests were carried out with low load (motor slip close to 0.3%), and others with high load (slip around 4%). The acquisition system was based on a National Instruments PCI6250 card, plus an external interface module with LEM Hall Effect sensors used as transducers. The acquired data was processed using Matlab R2015 software. The induction motor used mixed eccentricity, which produces great interharmonic content in the low part of the current spectrum, which, together with the abundant harmonic and interharmonic content in the high part of the spectrum present in the output of the inverters, allowed us analyzing situations with a multitude of nearby tones and similar amplitudes. The motor operated at steady state during 60 s long tests, and the sampling frequency was 80 kS/s. All measurements were made at the output of the inverters, with fundamental frequencies and harmonic contents different from those of the mains signal, so it was necessary to adapt the analysis system, based on IEC standards, and orient it to the measurement of the utility network; to the specific characteristics of the signals. Figure 9 shows the laboratory test bench. Figure 9. Laboratory test bench. Figure 10a shows the low part of the frequency response of the output current of the induction motor fed by a PowerFlex inverter with slip s ≈ 4% and a fundamental frequency of 45 Hz. Figure 10b shows the low part of the frequency response of the output voltage of the Altivar inverter working at 55 Hz and with low loaded motor (s ≈ 0.3%). The frequency responses were obtained based on the IEC standard, (using DFT, with spectral bars separated by 5 Hz), not yet grouped by frequency. It can be seen that the interharmonic content was much higher for the current signal (figure 10a) than for the voltage signal (figure 10b). Therefore, high values of the groupings and current rates containing those frequencies were to be expected, and a greater interaction between tones, which motivates an increase in the aggregation time necessary to obtain stable values, as explained before. On the other hand, the tone interaction was predicted to be lower in the case of figure 10b, since the voltage measured in that zone presents practically only harmonics (which do not interact with each other, as they do not produce spectral leakage). Figure 10. Low part of the frequency response of the supply signals from two inverters connected to an induction motor: (a) current with PowerFlex, (b) voltage with inverter Altivar. Figure 11 presents the time evolution, using 0.2 s long windows, of the harmonic distortion rates for low frequencies (THD (Total Harmonic Distortion) of current (Figure 11a) and voltage (Figure 11b)), measured at the output of the inverters of the same tests of Figure 10. RW was used in the graphs on the left and HW in the graphs on the right. Blue indicates the values without time aggregation or corresponding to each analysis window. In red, the values aggregated until each instant are shown so that it is possible to observe the value of any size of aggregation up to 60 s (duration of the test). The aggregated values for 3 s and 60 s, as well as the window number corresponding to each aggregation time, are highlighted in all graphs. Appl. Sci. 2019, 9, x FOR PEER REVIEW 17 of 21 Figure 10. Low part of the frequency response of the supply signals from two inverters connected to an induction motor: (a) current with PowerFlex, (b) voltage with inverter Altivar. Figure 11 presents the time evolution, using 0.2 s long windows, of the harmonic distortion rates for low frequencies (THD (Total Harmonic Distortion) of current (Figure 11.a) and voltage (Figure 11.b)), measured at the output of the inverters of the same tests of Figure 10. RW was used in the graphs on the left and HW in the graphs on the right. Blue indicates the values without time aggregation or corresponding to each analysis window. In red, the values aggregated until each instant are shown so that it is possible to observe the value of any size of aggregation up to 60 s (duration of the test). The aggregated values for 3 s and 60 s, as well as the window number corresponding to each aggregation time, are highlighted in all graphs. Figure 11. Time evolution of: (a) the THD current rate of the PowerFlex inverter, and (b) the THD voltage rate of the Altivar inverter, for the same tests shown in Figure 10. In tests whose spectra present harmonics surrounded by abundant interharmonics, of relatively large amplitudes and comparable to those of harmonics and close to them (as, for example, occurs in the test corresponding to Figure 10a), large differences were observed between the values found in each individual window for rates such as THD (blue graphs in Figure 11a). This is because the leakage produced by these interharmonics is also large, and when absorbed by nearby harmonics, vectorially adding to them, gives rise to variable amplitudes, and therefore, more aggregation time would be needed, as indicated in the previous sections. Thus, it was observed how the aggregated values obtained in the Figure 11a test were stabilized for a time greater than 3 s, which would justify the use of longer aggregation times. On the other hand, the rate measured in Figure 11.b reached a stable value more quickly, due to the lower interharmonic content of the analyzed signal (Figure 10.b), in which case the aggregation time of 3 s was sufficient. These tests prove experimentally that the aggregation time required for some parameters measured at the output of inverters may be greater than the 3 s indicated in the standard, and considerably less than the 10 min indicated in the same IEC standard for the next recommended time grouping. 7. Discussion Figure 11. Time evolution of: ( a ) the THD current rate of the PowerFlex inverter, and ( b ) the THD voltage rate of the Altivar inverter, for the same tests shown in Figure 10. In tests whose spectra present harmonics surrounded by abundant interharmonics, of relatively large amplitudes and comparable to those of harmonics and close to them (as, for example, occurs in the test corresponding to Figure 10a), large differences were observed between the values found in each individual window for rates such as THD (blue graphs in Figure 11a). This is because the leakage produced by these interharmonics is also large, and when absorbed by nearby harmonics, vectorially adding to them, gives rise to variable amplitudes, and therefore, more aggregation time would be needed, as indicated in the previous sections. Thus, it was observed how the aggregated values obtained in the Figure 11a test were stabilized for a time greater than 3 s, which would justify Appl. Sci. 2019,9, 4549 18 of 21 the use of longer aggregation times. On the other hand, the rate measured in Figure 11b reached a stable value more quickly, due to the lower interharmonic content of the analyzed signal (Figure 10b), in which case the aggregation time of 3 s was sufficient. These tests prove experimentally that the aggregation time required for some parameters measured at the output of inverters may be greater than the 3 s indicated in the standard, and considerably less than the 10 min indicated in the same IEC standard for the next recommended time grouping. 7. Discussion The correct measurement of the network harmonic content is important to characterizing the energy supplied, for example, at the output of frequency converters, as this type of equipment is the source of high harmonic and interharmonic content that makes analysis very challenging. The existing regulations establish procedures for adequate measurement, describing both the spectral groupings and the necessary time groupings, but problems may arise that make the measurements obtained unreliable. One of them is the instability and inaccuracy of the amplitude values obtained with DFTs in successive sampling windows, due to spectral leakage, and which affect the groupings and distortion rates based on IEC standards. A second problem is the possible occurrence of local peaks due to interharmonic tones that are distanced from each other by multiples of the spectral resolution, and therefore, are not affected by time aggregation, as a way of obtaining reliable RMS values. The evolution of the values of the groupings defined by the IEC standards has been studied to describe these problems and propose solutions. The study focused on the relative position between interharmonics and harmonics, and their relationship with the time of aggregation and type of window. Time aggregation is not necessary when a single frequency component is contained in the frequency grouping measured, since in that case, there is no interference between different components, and therefore, the RMS value obtained is stable and reliable. Examples of these frequency components are a tone present within the measured grouping, the spectral leakage received from another tone outside the grouping, or, if HW is used, a sideband to a tone. However, with more than one component within any of the groupings defined in the standards (such as several interharmonics whose leakages rotate at different speeds) each spectral bar will receive those leakages. Therefore, the total vector obtained in that bar will be the sum of the contributions of all the leakages, causing the variation of its amplitude in each successive analysis window. Therefore, it is convenient to perform time aggregation in all spectral groupings to minimize the effects of leakage on the resulting amplitudes, and to obtain a reliable and stable RMS value. Such time aggregation should be applied to all groups and subgroups, harmonics and interharmonics, and all distortion rates, as these rates are composed of those normalized groupings. That way, DFT amplitude variation caused by spectral leakage decreases, and the final aggregated value is closer to the correct RMS one. However, the ideal aggregation period Tw is unknown in practical applications or differs depending on the area of the spectrum, type of signal (either from the network or from the output of a converter), and the rest of the conditions of each test. Besides, the 61000-4-30 standard proposes aggregation time values as distant as 3 s to 2 h, so the specific duration of this aggregation time for each particular case is open to modification. Time aggregation must be adapted to the thermal time constants of the connected equipment. When thermal time constants are short, as in industrial environments, it is preferable to use the 3 s aggregation interval; the 10 min aggregation interval is best used to evaluate systems with longer time constants, such as the public electric network. For this reason, even based on quality standards, the necessary modifications must be made to adapt the values recommended in these standards to the particular case of measurements on systems consisting of frequency converters supplying induction motors. For all the above reasons, a solution has been proposed to the problems of instability and imprecision in the RMS values, obtained with the DFT according to IEC standards: the use of time aggregation with an increase in the aggregation time Appl. Sci. 2019,9, 4549 19 of 21 with respect to the 3 s recommended by the regulations for signals in industrial environments. This proposal improves the results for all cases with interacting tones. On the other hand, the sensitivity analysis of several tones interacting shows differences between RW and HW similar to those studied with a single tone, provided that an appropriate time aggregation is carried out beforehand. HW provides values closer to the ideals in interior areas and further away from the frequency groupings, whereas RW provides better results in the transition between groupings. In specific cases where the interacting tones are separated by multiples of the frequency resolution, local peaks are produced, which most often deviate from the correct value obtained for other sweep tones close to each singularity. This second problem can be solved by an appropriate combination of time aggregation with overlapping between successive analyzed windows. This approach provides an enhanced response for all harmonic and interharmonic positions of the tones present in the signal. Overlapping of 75% is an advisable value, for its being one of the most used, as indicated in [ 46 ], and for allowing the elimination of the most notable local peaks of RW and all the important ones of HW. Consequently, with the proposal presented in this work, which consists of carrying out an adequate time aggregation with overlapping, it is possible to obtain a response closer to the ideal in all the frequency groupings defined in the regulations, and thus obtain more reliable and precise measures in their related distortion rates. This is especially necessary for signals such as the output of electronic converters, which are rich in nearby tones, whose leakage can interact, causing this problem, especially those using some types of modulations, such as closed-loop or random modulations, or when connected to faulty motors that cause additional harmonic content. It has been experimentally proven that the aggregation time required for some parameters measured at the output of the tested drives may be greater than the 3 s indicated in the standard, and considerably less than the 10 min indicated in the same IEC standard for the next recommended time grouping. The duration of the tests carried out was 1 min because the thermal constants of the equipment tested resulted in aggregation times shorter than this time. It has also been verified that, in areas of the spectrum with stable harmonics and low interharmonic content, the aggregation time may be shorter. Author Contributions: Conceptualization, A.A.-G., O.D.-P., D.M.-S., and A.Z.-L.; data curation, A.A.-G.; methodology, A.A.-G., O.D.-P., and D.M.-S.; software, A.A.-G.; validation, D.M.-S.; writing—original draft, A.A-G.; writing—reviewing and editing, O.D.-P., D.M.-S., and A.Z.-L. Funding: This research was partially funded by Universidad de Valladolid. 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